TSH350
550MHz low noise current feedback amplifier
Features
Bandwidth: 550MHz in unity gain Quiescent current: 4.1mA Slew rate: 940V/s Input noise: 1.5nV/Hz Distortion: SFDR=-66dBc (10MHz, 1Vpp) 2.8Vpp minimum output swing on 100 load for a 5V supply Tested on 5V power supply SO-8 Pin connections (top view) SOT23-5
Applications
Communication & video test equipment Medical instrumentation ADC drivers
Output 1 VCC - 2 Non-Inv. In. 3
SOT23-5
5 VCC +
+4 Inv. In.
Description
The TSH350 is a current feedback operational amplifier using a very high-speed complementary technology to provide a bandwidth up to 410MHz while drawing only 4.1mA of quiescent current. With a slew rate of 940V/s and an output stage optimized for driving a standard 100 load, this circuit is highly suitable for applications where speed and power-saving are the main requirements. The TSH350 is a single operator available in the tiny SOT23-5 and SO-8 plastic packages, saving board space as well as providing excellent thermal and dynamic performance.
NC 1 Inv. In. 2 Non-Inv. In. 3 VCC - 4
SO-8
8 NC _ + 7 VCC + 6 Output 5 NC
June 2007
Rev 4
1/22
www.st.com 22
Absolute maximum ratings
T SH350
1
Absolute maximum ratings
Table 1.
Symbol VCC Vid Vin Tstg Tj Rthja Supply voltage (1) Differential input voltage Input voltage range
(3) (2)
Absolute maximum ratings (AMR)
Parameter Value 6 +/-0.5 +/-2.5 -65 to +150 150 250 150 80 28 500 830 2 0.5 200 60 1.5 1.5 200 Unit V V V C C C/W
Storage temperature Maximum junction temperature Thermal resistance junction to ambient SOT23-5 SO-8 Thermal resistance junction to case SOT23-5 SO-8 Maximum power dissipation(4) (@Tamb=25C) for Tj=150C SOT23-5 SO-8 HBM: human body model (5) pins 1, 4, 5, 6, 7 and 8 pins 2 and 3
Rthjc
C/W
Pmax
mW
kV
ESD
MM: machine model (6) pins 1, 4, 5, 6, 7 and 8 pins 2 and 3 CDM: charged device model(7) pins 1, 4, 5, 6, 7 and 8 pins 2 and 3 Latch-up immunity
V
kV mA
1. All voltage values are measured with respect to the ground pin. 2. Differential voltage is the non-inverting input terminal with respect to the inverting input terminal. 3. The magnitude of input and output voltage must never exceed VCC +0.3V. 4. Short-circuits can cause excessive heating. Destructive dissipation can result from short-circuits on all amplifiers. 5. Human body model: A 100pF capacitor is charged to the specified voltage, then discharged through a 1.5k resistor between two pins of the device. This is done for all couples of connected pin combinations while the other pins are floating. 6. Machine model: A 200pF capacitor is charged to the specified voltage, then discharged directly between two pins of the device with no external series resistor (internal resistor < 5). This is done for all couples of connected pin combinations while the other pins are floating. 7. Charged device model: all pins and the package are charged together to the specified voltage and then discharged directly to the ground through only one pin. This is done for all pins.
2/22
TSH350 Table 2.
Symbol VCC Vicm Toper Supply voltage
(1)
Absolute maximum ratings Operating conditions
Parameter Value 4.5 to 5.5 -VCC+1.5V to +VCC-1.5V -40 to + 85 Unit V V C
Common mode input voltage Operating free air temperature range
1. Tested in full production at 5V (2.5V) supply voltage.
3/22
Electrical characteristics
TSH350
2
Table 3.
Symbol
Electrical characteristics
Electrical characteristics for VCC = 2.5V, Tamb = 25C (unless otherwise specified)
Parameter Test conditions Min. Typ. Max. Unit
DC performance Vio Vio Iib+ Input offset voltage Offset voltage between both inputs Vio drift vs. temperature Non inverting input bias current DC current necessary to bias the input + Inverting input bias current DC current necessary to bias the input Common mode rejection ratio 20 log (Vic/Vio) Supply voltage rejection ratio 20 log (VCC/Vio) Power supply rejection ratio 20 log (VCC/Vout) Positive supply current DC consumption with no input signal Tamb Tmin < Tamb < Tmax Tmin < Tamb < Tmax Tamb Tmin < Tamb < Tmax Tamb Tmin < Tamb < Tmax Vic = 1V Tmin < Tamb < Tmax VCC=+3.5V to +5V Tmin < Tamb < Tmax AV = +1, VCC=100mV at 1kHz Tmin < Tamb < Tmax No load 68 56 0.8 1 0.9 12 13 1 2.5 60 dB 58 81 dB 78 51 dB 48 4.1 4.9 mA 20 35 V/C A A 4 mV
Iib-
CMR
SVR
PSR
ICC
Dynamic performance and output characteristics Transimpedance Output voltage/input current gain in open loop of a CFA. For a VFA, the analog of this feature is the open loop gain (AVD) -3dB bandwidth Frequency where the gain is 3dB below the DC gain AV Note: Gain bandwidth product criterion is not applicable for current-feedback-amplifiers Gain flatness @ 0.1dB Band of frequency where the gain variation does not exceed 0.1dB SR Slew rate Maximum output speed of sweep in large signal High level output voltage Vout = 1V, RL = 100 Tmin < Tamb < Tmax Small signal Vout=20mVpp AV = +1, RL = 100 AV = +2, RL = 100 AV = +10, RL = 100 AV = -2, RL = 100 Small signal Vout=100mVp AV = +1, RL = 100 Vout = 2Vpp, AV = +2, RL = 100 RL = 100 Tmin < Tamb < Tmax 1.44 170 270 k k
ROL
250
Bw
250
550 390 125 370
MHz
65
940 1.56 1.49
V/s V
VOH
4/22
TSH350 Table 3.
Symbol VOL
Electrical characteristics Electrical characteristics for VCC = 2.5V, Tamb = 25C (unless otherwise specified)
Parameter Low level output voltage Test conditions RL = 100 Tmin < Tamb < Tmax Output to GND Isink Shor t-circuit output current coming in the opTmin < Tamb < Tmax amp (see Figure 9) 135 Min. Typ. Max. Unit V
-1.53 -1.44 -1.49 205 195
Iout
mA Isource Output current coming out from the op-amp (see Figure 10) Output to GND Tmin < Tamb < Tmax -140 -210 -185
Noise and distortion eN Equivalent input noise voltage See Section 5: Noise measurements Equivalent input noise current (+) See Section 5: Noise measurements iN Equivalent input noise current (-) See Section 5: Noise measurements F = 100kHz 13 pA/ Hz F = 100kHz F = 100kHz 1.5 20 nV/ Hz pA/ Hz
SFDR
AV = +1, Vout = 1Vpp Spurious free dynamic range F = 10MHz The highest harmonic of the output spectrum F = 20MHz F = 50MHz when injecting a filtered sine wave F = 100MHz
-66 -57 -46 -42
dBc
Table 4.
Closed-loop gain and feedback components
Gain +10 -10 +2 2.5 -2 +1 -1 300 820 300 370 550 350 70 65 120 Rfb () 300 300 300 -3dB Bw (MHz) 125 120 390 0.1dB Bw (MHz) 22 20 110
VCC (V)
5/22
Electrical characteristics
TSH350
Figure 1.
Frequency response, positive gain Figure 2.
Frequency response, negative gain
24 22 20 18 16 14 12 10 8 6 4 2 0 -2 -4 Sm a ll Signal -6 V cc = 5 V -8 Load=10 0 - 10 1M
G a i n =+1 0
G a i n =+4
G a i n =+2
G a i n =+1
1 0M
1 00 M
1G
24 22 20 18 16 14 12 10 8 6 4 2 0 -2 -4 Sm a ll Signal -6 V cc = 5 V -8 Load=10 0 - 10 1M
G a i n =- 1 0
G a i n =- 4
Gain (dB)
Gain (dB)
G a i n =- 2
G a i n =- 1
1 0M
1 00 M
1G
Frequency (Hz)
Frequency (Hz)
Figure 3.
12 ,1
Compensation, gain=+4
Figure 4.
6 ,2
Compensation, gain=+2
12 ,0
6 ,1
Gain Flatness (dB)
Gain Flatness (dB)
6 ,0
11 ,9
5 ,9
Vin
+
Vin
+ -
Vo u t
Vou t
11 ,8
4pF
-
5 ,8
300R 100R
8k2 2p F
300 R 100R
11 ,7
Gain=+4, Vcc=5V, Small Signal
5 ,7
Gain=+2, Vcc=5V, Small Signal
11 ,6 1M
10 M
10 0 M
5 ,6 1M
10 M
1 0 0M
1G
Frequency (Hz)
Frequency (Hz)
Figure 5.
Frequency response vs. capacitor load
C -L oa d = 1p F R - is o = 2 2 o h m s
Figure 6.
Step response vs. capacitor load
10 8 6
3
C -L o ad = 1 p F R -i s o = 2 2 oh m s 2
Output step (Volt)
4
Gain (dB)
2 0 -2 -4 -6 -8 - 10 1M
300R 300R 1k C-Load Vin
+ -
C - L oa d= 10 p F R - is o = 3 9 o h m s
C -L oa d = 1 0p F R - is o = 3 9 o h m s 1
C - Lo a d= 22 pF R - is o = 2 7 o h m s
Vin
+ -
Vout R-iso
C -L oa d = 22 p F R - is o = 2 7 o h m s
Vout R-iso 1k C-Load
0
300R 300R
Gain=+2, Vcc=5V, Small Signal
Gain=+2, Vcc=5V, Small Signal
1 0M
1 00 M
1G
-1 0 ,0 s
2 ,0 n s 4 , 0 n s 6 , 0 n s 8 ,0 n s 1 0 , 0 n s 1 2 , 0 n s 1 4 ,0 n s 1 6 ,0 n s 1 8 ,0 n s 2 0 ,0 n s
Frequency (Hz)
Time (ns)
6/22
TSH350
Electrical characteristics
Figure 7.
2 ,0
Slew rate
Figure 8.
4 ,0
Output amplitude vs. load
M ax. Output Amplitude (Vp-p)
Output Response (V)
3 ,5
1 ,5
1 ,0
3 ,0
0 ,5
2 ,5
0 ,0 -2 ns - 1n s 0s 1n s
G a i n =+ 2 V cc = 5 V Load=100
2ns 3 ns
2 ,0 10 10 0 1k 1 0k
G a in = + 2 V c c =5 V Load=100
10 0 k
Time (ns)
Load (ohms)
Figure 9.
300
Isink
+ 2 . 5V VOL
Figure 10. Isource
0
without lo ad
250
+
-1 V
-5 0
I sin k V - 2. 5V
_
Isink (mA)
Amplifier in open loop w ithout load
150
Isource (mA)
200
RG
- 10 0
- 15 0
+
+2 . 5 V VOH
without lo ad
100
- 20 0
+ 1V
_
- 2. 5V
Iso urc e V
50
- 25 0
RG
Amplifier in open loop w ithout load
0 - 2, 0
- 1 ,5
-1 ,0
-0 ,5
0 ,0
- 30 0 0 ,0
0,5
1, 0
1, 5
2, 0
V (V)
V (V)
Figure 11. Input current noise vs. frequency
70
Figure 12. Input voltage noise vs. frequency
4.0
60
Pos. Current N o ise
3.5
in (pA/sqrt(Hz))
50
en (nV/sqrt(Hz))
1M 10M
3.0
40
Neg. Current N o ise
2.5
30
2.0
20
1.5
10 1k
10k
100k
1.0 1k
10k
100k
1M
10M
Frequency (Hz)
Frequency (Hz)
7/22
Electrical characteristics
TSH350
Figure 13. Quiescent current vs. VCC
5 4 3
Icc(+)
Figure 14. Distortion vs. output amplitude
0 -5 -10 -15 -20
HD2 & HD3 (dBc)
2
-25 -30 -35 -40 -45 -50 -55 -60 -65 -70
Icc (mA)
1 0 -1 -2 -3 -4 -5 1 ,2 5
Icc(-)
G a in = + 2 V c c= 5 V Input to ground, no load
HD2
HD3
-75 -80
1 ,7 5 2 ,0 0 2 ,2 5 2 ,5 0
G a in = + 2 V c c =5 V F =3 0 MH z L oad=100
1 2 3 4
1 ,5 0
0
+/-Vcc (V)
Output Amplitude (Vp-p)
Figure 15. Distortion vs. output amplitude
-20 -25 -30 -35 -40
Figure 16. Noise figure
40 35 30 25
HD2 & HD3 (dBc)
-45 -50 -55 -60 -65 -70 -75 -80 -85 -90 -95 -100 0 1 2 3
NF (dB)
G a in = + 2 V c c =5 V F= 1 0 MH z Load=100
4
HD2
20 15 10 5 0
HD3
G a in = ? V c c= 5 V
1 10 100 1k 10k 100k
Output Amplitude (Vp-p)
Rsource (ohms)
Figure 17. Distortion vs. output amplitude
-20 -25 -30 -35 -40
Figure 18. Output amplitude vs. frequency
5
4
HD2 & HD3 (dBc)
-50 -55 -60 -65 -70 -75 -80 -85 -90 -95 -100 0 1 2 3
Vout max. (Vp-p)
G a in = + 2 V c c =5 V F= 2 0 MH z Load=100
4
-45
HD2
3
HD3
2
1
0 1M
G a i n =+ 2 V cc = 5 V Load=10 0
1 0M 1 00 M 1G
Output Amplitude (Vp-p)
Frequency (Hz)
8/22
TSH350
Electrical characteristics
Figure 19. Reverse isolation vs. frequency
0
Figure 20. SVR vs. temperature
90 85
-2 0 80
Isolation (dB)
SVR (dB)
-4 0
75 70 65 60
-6 0
-8 0
-1 0 0 1M
Sm all Signal V c c= 5 V Lo ad=100
10 M 10 0 M 1G
55 50
G a in = + 1 V c c =5 V Lo ad=100
-4 0 -2 0 0 20 40 60 80 10 0 12 0
Frequency (Hz)
Temperature (C)
Figure 21. Bandwidth vs. temperature
550
Figure 22. ROL vs. temperature
340
500
320
450
300
Bw (MHz)
400
ROL (M)
280 260 240 220 200
350
300
G a in = + 1 250 Vcc=5V Load=100
200 -4 0 -2 0 0 20 40 60 80 10 0 12 0
Open Loop Vcc=5V
-40 -20 0 20 40 60 80 100 120
Temperature (C)
Temperature (C)
Figure 23. CMR vs. temperature
70
Figure 24. Ibias vs. temperature
14
68 12 66 10 64 8
Ib(+)
CMR (dB)
IBIAS (A)
62 60 58 56
6 4 2 0
Ib(-)
54 52 50
Gain=+1 Vcc=5V Load=100
-40 -20 0 20 40 60 80 100 120
-2 -4
Gain=+1 Vcc=5V Load=100
-40 -20 0 20 40 60 80 100 120
Temperature (C)
Temperature (C)
9/22
Electrical characteristics
TSH350
Figure 25. Vio vs. temperature
10 0 0
Figure 26. ICC vs. temperature
6 4
800 2
Icc(+)
VIO (micro V)
ICC (mA)
600
0 -2
Icc(-)
400
-4 -6
200
Open Loop V c c= 5 V Lo ad=100
-4 0 -2 0 0 20 40 60 80 10 0 1 20
Gain=+1 Vcc=5V -8 no Load In+/In- to GND
-10 -40 -20 0 20 40 60 80 100 120
0
Temperature (C)
Temperature (C)
Figure 27. VOH and VOL vs. temperature
2
Figure 28. Iout vs. temperature
300 200
1 0
VO H
Isource
100
VOH & OL (V)
-1 -2 -3 -4
VO L
Iout (mA)
0 -100
Isink
-200 -300 -400 0 20 40 60 80
Gain=+1 Vcc=5V Load=100
-20
Output: short-circuit Gain=+1 Vcc=5V
-40 -20 0 20 40 60 80 100 120
-5 -40
Temperature (C)
Temperature (C)
10/22
TSH350
Evaluation boards
3
Evaluation boards
An evaluation board kit optimized for high-speed operational amplifiers is available (order code: KITHSEVAL/STDL). As well as a CD-ROM containing datasheets, articles, application notes and a user manual, the kit includes the following evaluation boards:
SOT23_SINGLE_HF BOARD Board for the evaluation of a single high-speed op-amp in SOT23-5 package. SO8_SINGLE_HF Board for the evaluation of a single high-speed op-amp in SO-8 package. SO8_DUAL_HF Board for the evaluation of a dual high-speed op-amp in SO-8 package. SO8_S_MULTI Board for the evaluation of a single high-speed op-amp in SO-8 package in inverting and non-inverting configuration, dual and single supply.
SO14_TRIPLE Board for the evaluation of a triple high-speed op-amp in SO-14 package with video application considerations.
Board material:
2 layers FR4 ( r=4.6) epoxy 1.6mm copper thickness: 35m
Figure 29. Evaluation kit for high-speed op-amps
11/22
Power supply considerations
TSH350
4
Power supply considerations
Correct power supply bypassing is very important for optimizing performance in highfrequency ranges. Bypass capacitors should be placed as close as possible to the IC pins to improve high-frequency bypassing. A capacitor greater than 1F is necessary to minimize the distortion. For better quality bypassing, a capacitor of 10nF can be added which should also be placed as close as possible to the IC pins. Bypass capacitors must be incorporated for both the negative and the positive supply.
Note:
On the SO8_SINGLE_HF board, these capacitors are C6, C7, C8, C9. Figure 30. Circuit for power supply bypassing
+VCC + 10nF
10F
+ 10nF
10F + -VCC
Single power supply
In the event that a single supply system is used, biasing is necessary to obtain a positive output dynamic range between 0V and +VCC supply rails. Considering the values of VOH and VOL, the amplifier will provide an output swing from +0.9V to +4.1V on a 100 load. The amplifier must be biased with a mid-supply (nominally +VCC/2), in order to maintain the DC component of the signal at this value. Several options are possible to provide this bias supply, such as a virtual ground using an operational amplifier or a two-resistance divider (which is the cheapest solution). A high resistance value is required to limit the current consumption. On the other hand, the current must be high enough to bias the non-inverting input of the amplifier. If we consider this bias current (35A maximum) as 1% of the current through the resistance divider, to keep a stable mid-supply, two resistances of 750 can be used. The input provides a high-pass filter with a break frequency below 10Hz which is necessary to remove the original 0 volt DC component of the input signal, and to fix it at +VCC/2. Figure 31 illustrates a 5V single power supply configuration for the SO8_S_MULTI evaluation board (see Evaluation boards on page 11).
12/22
TSH350
Power supply considerations A capacitor CG is added in the gain network to ensure a unity gain in low frequency to keep the right DC component at the output. CG contributes to a high-pass filter with Rfb//RG and its value is calculated with a consideration of the cut off frequency of this low-pass filter. Figure 31. Circuit for +5V single supply (using evaluation board SO8_S_MULTI)
+5V 10F IN +5V R1 750 Rfb R2 750 + 1F 10nF + RG CG Rin 1k
+
_
100F
OUT 100
13/22
Noise measurements
TSH350
5
Noise measurements
The noise model is shown in Figure 32:
eN is the input voltage noise of the amplifier iNn is the negative input current noise of the amplifier iNp is the positive input current noise of the amplifier
Figure 32. Noise model
+
R3
iN+
_
output HP3577 Input noise: 8nV/Hz
N3
iN-
eN
N2
R1
R2
N1
The thermal noise of a resistance R is
4kTRF
where F is the specified bandwidth. On a 1Hz bandwidth the thermal noise is reduced to:
4kTR
where k is the Boltzmann's constant, equal to 1,374.10-23J/K. T is the temperature (K). The output noise eNo is calculated using the Superposition Theorem. However, eNo is not the simple sum of all noise sources, but rather the square root of the sum of the square of each noise source, as shown in Equation 1: Equation 1
eNo = V1 + V2 + V3 + V4 + V5 + V6
2 2 2 2 2 2
14/22
TSH350 Equation 2
Noise measurements
2 2 2 2 2 2 2 2 2 R2 R22 e N o = e N × g + i N n × R 2 + i N p × R 3 × g + ------- × 4 k T R 1 + 4 k T R 2 + 1 + ------- × 4 k T R 3 R1 R1
The input noise of the instrumentation must be extracted from the measured noise value. The real output noise value of the driver is: Equation 3
eNo =
( Measured ) ( instrumentation )
2 2
The input noise is called equivalent input noise because it is not directly measured but is evaluated from the measurement of the output divided by the closed loop gain (eNo/g). After simplification of the fourth and the fifth term of Equation 2 we obtain: Equation 4
2 2 2 2 2 2 2 2 R22 e N o = e N × g + i N n × R 2 + i N p × R 3 × g + g × 4 k T R 2 + 1 + ------- × 4 k T R 3 R1
Measurement of the input voltage noise eN
If we assume a short-circuit on the non-inverting input (R3=0), from Equation 4 we can derive: Equation 5
eNo = eN × g + iNn × R2 + g × 4kTR2
2 2 2 2
In order to easily extract the value of eN, the resistance R2 will be chosen to be as low as possible. In the other hand, the gain must be large enough: R3=0, gain: g=100
Measurement of the negative input current noise iNn
To measure the negative input current noise iNn, we set R3=0 and use Equation 5. This time, the gain must be lower in order to decrease the thermal noise contribution: R3=0, gain: g=10
Measurement of the positive input current noise iNp
To extract iNp from Equation 3, a resistance R3 is connected to the non-inverting input. The value of R3 must be chosen in order to keep its thermal noise contribution as low as possible against the iNp contribution: R3=100W, gain: g=10
15/22
Intermodulation distortion product
TSH350
6
Intermodulation distortion product
The non-ideal output of the amplifier can be described by the following series:
Vo u t = C0 + C1 Vi n + C2 V
2 in
+ ...+ Cn V
n
in
where the input is Vin=Asint, C0 is the DC component, C1(Vin) is the fundamental and Cn is the amplitude of the harmonics of the output signal Vout. A one-frequency (one-tone) input signal contributes to harmonic distortion. A two-tone input signal contributes to harmonic distortion and to the intermodulation product. The study of the intermodulation and distortion for a two-tone input signal is the first step in characterizing the driving capability of multi-tone input signals. In this case:
V i n = A sin 1 t + A sin 2 t
then:
V o u t = C 0 + C 1 ( A sin 1 t + A sin 2 t ) + C 2 ( A sin 1 t + A sin 2 t ) ...+ C n ( A sin 1 t + A sin 2 t )
2 n
From this expression, we can extract the distortion terms, and the intermodulation terms from a single sine wave:
second order intermodulation terms IM2 by the frequencies (1-2) and (1+ 2) with an amplitude of C2A2 third order intermodulation terms IM3 by the frequencies (21-2), (21+ 2), (- 1+22) and (1+ 2) with an amplitude of (3/4)C3A3 2
The intermodulation product of the driver is measured by using the driver as a mixer in a summing amplifier configuration (see Figure 33). In this way, the non-linearity problem of an external mixing device is avoided. Figure 33. Inverting summing amplifier (using evaluation board SO8_S_MULTI)
Vin1 Vin2
R1
Rfb
R2
_
Vout
+
100
R
16/22
TSH350
Inverting amplifier biasing
7
Inverting amplifier biasing
A resistance is necessary to achieve good input biasing, such as resistance R shown in Figure 34. The magnitude of this resistance is calculated by assuming the negative and positive input bias current. The aim is to compensate for the offset bias current, which could affect the input offset voltage and the output DC component. Assuming Iib-, Iib+, Rin, Rfb and a zero volt output, the resistance R is:
Ri × Rf b R = ------n---------------Ri n + Rf b
Figure 34. Compensation of the input bias current
Rfb Rin
I ib-
_
VCC+ Output
+
I ib+ R VCC-
Load
17/22
Active filtering
TSH350
8
Active filtering
Figure 35. Low-pass active filtering, Sallen-Key
C1
R1 IN
R2 C2
+
OUT
_
100
RG
R fb 910
From the resistors Rfb and RG we can directly calculate the gain of the filter in a classic noninver ting amplification configuration:
Rf b A V = g = 1 + -------Rg
We assume the following expression as the response of the system:
V o u tj --T j = --------------- = -------------------g-----------------V i nj j--- ( j ) 2 1 + 2 - + ----------c 2 c
The cut-off frequency is not gain-dependent and so becomes:
1 c = -----------------------------------R1R2C1C2
The damping factor is calculated by the following expression:
1 = -- c ( C 1 R 1 + C 1 R 2 + C 2 R1 C 1 R 1 g ) 2
The higher the gain, the more sensitive the damping factor is. When the gain is higher than 1, it is preferable to use some very stable resistor and capacitor values. In the case of R1=R2=R:
Rf b 2 C 2 C 1 -------R - = ------------------------------g 2 C1 C2
Due to a limited selection of values of capacitors in comparison with resistors, we can set C1=C2=C, so that:
Rf b 2 R 2 R 1 -------R = ------------------------------g -2 R1 R2
18/22
TSH350
Package information
9
Package information
Figure 36. SOT23-5 package mechanical data
Dimensions Ref. Min. Millimeters Typ. Max. Min. Mils Typ. Max.
A A1 A2 b C D E E1 e e1 L
0.90 0.00 0.90 0.35 0.09 2.80 2.60 1.50 0.95 1.9 0.35
1.45 0.15 1.30 0.50 0.20 3.00 3.00 1.75
35.4 0.00 35.4 13.7 3.5 110.2 102.3 59.0 37.4 74.8
57.1 5.9 51.2 19.7 7.8 118.1 118.1 68.8
0.55
13.7
21.6
19/22
Package information Figure 37. SO-8 package mechanical data
Dimensions Ref. Min. Millimeters Typ. Max. Min. Inches Typ.
TSH350
Max.
A A1 A2 b c D H E1 e h L k ccc 0.25 0.40 1 0.10 1.25 0.28 0.17 4.80 5.80 3.80 4.90 6.00 3.90 1.27
1.75 0.25 0.004 0.049 0.48 0.23 5.00 6.20 4.00 0.011 0.007 0.189 0.228 0.150 0.193 0.236 0.154 0.050 0.50 1.27 8 0.10 0.010 0.016 1
0.069 0.010
0.019 0.010 0.197 0.244 0.157
0.020 0.050 8 0.004
20/22
TSH350
Ordering information
10
Ordering information
Table 5. Order codes
Temperature range Package Packing Marking
Part number
TSH350ILT TSH350ID TSH350IDT -40C to +85C
SOT23-5 SO-8 SO-8
Tape & reel Tube Tape & reel
K305 TSH350I TSH350I
11
Revision history
Date Revision Changes
1-Oct-2004 10-Dec-2004 21-Jun-2005 8-Jun-2007
1 2 3 4
First release corresponding to Preliminary Data version of datasheet. Release of mature product datasheet. In Table 1 on page 2, Rthjc thermal resistance junction to ambient replaced by thermal resistance junction to case. Format update.
21/22
TSH350
Please Read Carefully:
Information in this document is provided solely in connection with ST products. STMicroelectronics NV and its subsidiaries ("ST") reserve the right to make changes, corrections, modifications or improvements, to this document, and the products and services described herein at any time, without notice. All ST products are sold pursuant to ST's terms and conditions of sale. Purchasers are solely responsible for the choice, selection and use of the ST products and services described herein, and ST assumes no liability whatsoever relating to the choice, selection or use of the ST products and services described herein. No license, express or implied, by estoppel or otherwise, to any intellectual property rights is granted under this document. If any part of this document refers to any third party products or services it shall not be deemed a license grant by ST for the use of such third party products or services, or any intellectual property contained therein or considered as a warranty covering the use in any manner whatsoever of such third party products or services or any intellectual property contained therein.
UNLESS OTHERWISE SET FORTH IN ST'S TERMS AND CONDITIONS OF SALE ST DISCLAIMS ANY EXPRESS OR IMPLIED WARRANTY WITH RESPECT TO THE USE AND/OR SALE OF ST PRODUCTS INCLUDING WITHOUT LIMITATION IMPLIED WARRANTIES OF MERCHANTABILITY, FITNESS FOR A PARTICULAR PURPOSE (AND THEIR EQUIVALENTS UNDER THE LAWS OF ANY JURISDICTION), OR INFRINGEMENT OF ANY PATENT, COPYRIGHT OR OTHER INTELLECTUAL PROPERTY RIGHT. UNLESS EXPRESSLY APPROVED IN WRITING BY AN AUTHORIZED ST REPRESENTATIVE, ST PRODUCTS ARE NOT RECOMMENDED, AUTHORIZED OR WARRANTED FOR USE IN MILITARY, AIR CRAFT, SPACE, LIFE SAVING, OR LIFE SUSTAINING APPLICATIONS, NOR IN PRODUCTS OR SYSTEMS WHERE FAILURE OR MALFUNCTION MAY RESULT IN PERSONAL INJURY, DEATH, OR SEVERE PROPERTY OR ENVIRONMENTAL DAMAGE. ST PRODUCTS WHICH ARE NOT SPECIFIED AS "AUTOMOTIVE GRADE" MAY ONLY BE USED IN AUTOMOTIVE APPLICATIONS AT USER'S OWN RISK.
Resale of ST products with provisions different from the statements and/or technical features set forth in this document shall immediately void any warranty granted by ST for the ST product or service described herein and shall not create or extend in any manner whatsoever, any liability of ST.
ST and the ST logo are trademarks or registered trademarks of ST in various countries. Information in this document supersedes and replaces all information previously supplied. The ST logo is a registered trademark of STMicroelectronics. All other names are the property of their respective owners.
2007 STMicroelectronics - All rights reserved STMicroelectronics group of companies Australia - Belgium - Brazil - Canada - China - Czech Republic - Finland - France - Germany - Hong Kong - India - Israel - Italy - Japan Malaysia - Malta - Morocco - Singapore - Spain - Sweden - Switzerland - United Kingdom - United States of America www.st.com
22/22
|
