AN437 Application note
RC snubber circuit design for TRIACs
Introduction
When a TRIAC controls inductive loads, the mains voltage and the load current are not in phase. To limit the slope of the reapplied voltage and ensure right TRIAC turn-off, designer usually used a snubber circuit connected in parallel with the TRIAC. This circuit can also be used to improve TRIAC immunity to fast transient voltages. The subject of this paper is, first of all, to analyze the snubber circuit functions and to propose a method for snubber circuit design in order to improve turn-off commutation.
Contents
1 Snubber circuit functions and drawback . . . . . . . . . . . . . . . . . . . . . . . . 2
1.1 Turn-off improvement . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 2
1.1.1 1.1.2 TRIAC turn-off reminder . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 2 Snubber circuit benefit at TRIAC turn-off . . . . . . . . . . . . . . . . . . . . . . . . . 3
1.2 1.3 1.4
Overvoltage limitation at turn-off . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 4 Immunity to fast voltage transient improvement . . . . . . . . . . . . . . . . . . . . . 5 Turn-on stress due to snubber circuit discharge . . . . . . . . . . . . . . . . . . . . . 5
2
How to design snubber circuit for turn-off improvement . . . . . . . . . . . 7
2.1 2.2 Step response of an RLC series circuit . . . . . . . . . . . . . . . . . . . . . . . . . . . 7 RC snubber circuit design . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 9
2.2.1 2.2.2 Is the snubber circuit required? . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 9 Resistor and capacitor snubber circuit design . . . . . . . . . . . . . . . . . . . . 10
3
Conclusion . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 14
Appendix A RLC series circuit step response explanation . . . . . . . . . . . . . . . . 15 Revision history . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 17
October 2007
Rev 2
1/18
www.st.com
Snubber circuit functions and drawback
AN437
1
1.1
1.1.1
Snubber circuit functions and drawback
Turn-off improvement
TRIAC turn-off reminder
When a TRIAC switches from on-state to off-state, the current passes through zero and the supply voltage is reapplied instantaneously across the structure. In certain conditions, the component is not able to block this voltage and then turns on spontaneously. Indeed, a TRIAC can be compared to two Thyristors mounted in back-to-back and coupled with a single control area. To trigger the two Thyristors, the control area overlaps the two conduction areas. During the conduction time, a certain quantity of charges is injected into the structure. These charges disappear by recombination during the current decrease and by extraction after the turn-off with the reverse recovery current (refer to Figure 1). Nonetheless, an excess of charge remains, particularly in the neighboring regions of the gate, which can induce the triggering of the other conduction area when the mains voltage is reapplied across the TRIAC (refer to Figure 2). Figure 1. TRIAC turn-off on inductive load - suitable turn-off Figure 2. TRIAC turn-off on inductive load - spurious triggering
dV/dtOFF
VMains (100 V/div) VT (100 V/div)
VT (50 V/div)
Recover y current
IT (10 mA/div)
IT (10 mA/div)
dI/dtOFF
A spurious triggering depends on:
The slope of the decreasing current, called the turn-off dI/dt or dI/dtOFF. This parameter determines the quantity of charges which remains, when the current drops to zero, and which could be injected in the gate area or in the opposite Thyristor. The slope of the reapplied voltage, called the turn-off dV/dt or dV/dtOFF. This parameter defines the capacitive current which could be injected through the gate.
2/18
AN437
Snubber circuit functions and drawback
1.1.2
Snubber circuit benefit at TRIAC turn-off
The TRIAC turn-off behavior is characterized by the datasheet curve between the critical rate of decrease of commutating on-state current ((dI/dt)c) and the critical rate of rise of commutation off-state voltage ((dV/dt)c) (refer to Figure 3). These parameters are specified for the maximum operating junction temperature (worst case). In practice, the current waveform, and thus the slope of the decreasing current, is imposed by the load. The user can then only limit the slope of the reapplied voltage. Indeed, by adding an snubber circuit across the TRIAC, the circuit time response is increased and thus, dV/dtOFF is decreased (refer to Figure 3). Figure 3. (dI/dt)c versus (dV/dt)c curve for Z01 standard TRIACs and snubber circuit impact
Load
C
VMains
IT VT
Area of spurious firing at commutation
R
Safe area
Operating point with RC snubber Operating point
An RC snubber circuit must be used when there is a risk of TRIAC spurious triggering, i.e. when the dI/dtOFF - dV/dtOFF couple, measured in the application, is higher than the TRIAC datasheet values, (dI/dt)c at a given (dV/dt)c. Figure 4 shows the turn-off behavior of a Z0103 standard TRIAC which controls a 26 W drain pump. Without snubber circuit and for the maximum junction temperature (110 C), a spurious triggering appears at turn-off. Indeed, the measured (dI/dt)OFF and (dV/dt)OFF values, equal respectively to 0.13 A/ms and 10 V/s, are higher than the guarantee (dI/dt)c (dV/dt)c point (only 7 V/s @ 0.13 A/ms, see Figure 3). Thanks to an RC snubber circuit (10 nF and 2.7 k), the slope of the reapplied voltage can be limited to 1.5 V/s and thus spurious triggering at turn-off can be avoided (see Figure 3 and Figure 4).
3/18
Snubber circuit functions and drawback Figure 4.
AN437
Z0103 TRIAC turn-off on inductive load without and with snubber circuit (C = 10 nF and R = 2.7 k)
Without snubber :dV/dtOFF
IT (50 mA/div)
With snubber
VT (100 V/div)
The snubber circuit design, detailed in Section 2: How to design snubber circuit for turn-off improvement, is a trade-off between the maximum peak off-state voltage under pulse conditions (VDSM / VRSM), the critical slope of reapplied voltage ((dV/dt)c) and the turn-on stress (dI/dt). When low load inductances are controlled or, low damping factor or low slope of reapplied voltage are considered, the snubber circuit design can lead to choose a low snubber resistance value. To reduce the snubber capacitance discharge at turn-on, the resistance value is limited to a minimum value (refer to Section 1.4).
1.2
Overvoltage limitation at turn-off
When a TRIAC controls low root-mean-square currents inductive loads, an overvoltage could occur when the current reaches the holding current (IH) (refer to Figure 5). If the maximum value of the overvoltage (VM) exceeds the maximum peak off-state voltage under pulse conditions (VDSM / VRSM), the TRIAC may conduct without any gate current or may be even damaged. The protections against overvoltage at turn-off are:
A clamping strategy - use a varistor or an ACSTM / ACST (refer to AN1172 about protected AC SwitchTM). A damping strategy - a snubber circuit. An RC snubber circuit limits the slope of the voltage rise and could maintain the overvoltage at a lower value than the maximum allowed value. Overvoltage at TRIAC turn-off with and without snubber circuit (C = 10 nF and R = 2.7 k)
VM = 660 V
IT (20 mA/div)
Figure 5.
Without snubber
IH
VM = 140 V With snubber
VT (100 V/div)
4/18
AN437
Snubber circuit functions and drawback
1.3
Immunity to fast voltage transient improvement
Electrical noise may appear on the mains and generates across the TRIAC fast voltage variations, as described in IEC 61000-4-4 standard. Fast voltage variations can create a gate current (IG), due to the junction capacitance between A2 and the gate, and could trigger the TRIAC. The maximum rate of rise of offstate voltage that a TRIAC is able to withstand without turning on is called the static dV/dt. A spurious triggering due to static dV/dt is not dangerous for a component. The aim of the snubber circuit is to reduce the static dV/dt at a lower level than the dV/dt specified in the datasheet to avoid spurious triggering. An RC snubber circuit improves the TRIAC immunity against fast voltage transients. For example, regarding to the standard IEC 61000-4-4, a Z0109 standard TRIAC has a typical immunity level of about 0.7 kV, without any snubber circuit. With a snubber circuit (1 nF and 47 ), the Z0109 immunity level can reach 4.0 kV. Designers must manage the following trade-off to choose the suitable RC snubber circuit:
Reduce dV/dt rates: the snubber capacitance must be high and the snubber resistance must be low; Reduce dI/dt rate at turn-on (refer to Section 1.4): the snubber capacitance must be low and the snubber resistance must be high.
1.4
Turn-on stress due to snubber circuit discharge
The snubber circuit design can lead to low resistance value. However, the snubber resistor reduces the rate of current rise at turn-on (dI/dtON) during the capacitor discharge. An higher dI/dtON than the dI/dt specified in the datasheet may damage the TRIAC. The rate of current rise is directly proportional to the initial capacitance voltage and inversely proportional to the series inductances of the board and the snubber resistor. The rate of current rise depends also on the turn-on speed of the TRIAC, the triggering quadrants and the gate current amplitude. So, there is no simple way to predict the rate of current rise. Usually, the inductance of the circuit layout is very low, in the range of few nH. Indeed, to optimize the snubber circuit efficiency, the snubber circuit must be located very close to the TRIAC (tracks length lower than 2 cm). From datasheet specifications, there are three ranges of maximum dI/dt:
dI/dt = 20 A/s: for low current rating of TRIACs (0.8 A and 1 A). dI/dt = 50 A/s: for the other TRIACs (4 A up to 40 A). dI/dt = 100 A/s: for some ACSTs (6 A up to 12 A).
To keep the dI/dtON below 50 A/s for TRIACs and below 100 A/s for ACSTs, the snubber resistance must be typically higher than 47 (refer to Figure 6). For a 20 A/s maximum dI/dt, the minimum resistance value is about 620 . Therefore, depending on the component used, some tests should be performed to define accurately the minimum resistance value.
5/18
Snubber circuit functions and drawback Figure 6. Typical snubber circuit discharge (C = 10 nF and R = 47 ) with BTA/BTB16 TRIAC at peak mains voltage (quadrant 3, IG = 2 x IGT)
IT (1 A/div)
AN437
dI/dtON = 50 A/ s
IMax.
VT (100 V/div)
VMax. = 320 V
6/18
AN437
How to design snubber circuit for turn-off improvement
2
How to design snubber circuit for turn-off improvement
Step response of an RLC series circuit
The RSCS snubber circuit makes up a resonant circuit with an inductive load (refer L and R on Figure 7). At turn-off, the snubber circuit limits the slope of the reapplied voltage (dV/dtOFF) but generates an overvoltage (VP). The snubber circuit design results in a tradeoff to respect both the reapplied voltage slope ((dV/dt)c) and the maximum peak off-state voltage under pulse conditions (VDSM / VRSM). The electrical circuit analyzed in this paragraph is given by Figure 7. Figure 7. Application circuit and its equivalent diagram at turn-off
Application circuit
Load L VMains G IG R IT VT RS CS VCs
E
2.1
Equivalent diagram at turn-off
Load L R
IT RS VT CS VCs
For a second order linear differential equation with a step function input, the voltage variation across the snubber capacitance (VCs(t)) and the TRIAC (VT(t)) is given by:
Equation 1
1 0
2
·
d V Cs ( t ) dt
2
2
+
2 . dV Cs ( t ) · + V Cs ( t ) = E 0 dt
Equation 2
VT ( t) = R S · C S · dV Cs ( t ) dt + V Cs ( t )
With damping factor:
Equation 3
=
(R S + R )( ) 2
·
CS (F ) L(H )
Undamped natural resonance:
Equation 4
0 ( rad / s ) = 1 L ( H ) ·C S ( F )
7/18
How to design snubber circuit for turn-off improvement Final voltage value:
AN437
Equation 5
E= 2 · VRMS · sin( ) with sin( ) = L· 2 + (L · ) 2 R
V RMS : mains rms voltage
Snubber circuit divider ratio:
Equation 6
M= RS RS + R
By solving the second order linear differential equation according to the damping factor and initial conditions (refer to Appendix A: RLC series circuit step response explanation), two diagrams can be defined. These diagrams give the slope of the voltage rise (dV/dtOFF) and the peak voltage (VP) according to the damping factor () and the load resistance (M) (refer to Figure 8). The voltage rise slope (dV/dtOFF) is defined as the maximum instantaneous voltage rise slope. Figure 8. Trade-off between normalized peak voltage (Z = VP/E), normalized voltage rise slope (K = dV/dtOFF/(E x 0)) according to damping factor () and the divider ratio (M)
2 1.9 1.8 1.7 1.6 1.5 1.4 1.3 1.2 1.1 1 0 0.2 0.4 0.6 0.8 1 1.2 1.4 1.6 1.8 2 M=1 M = 0.75 M = 0.5 M = 0.25 M=0
Z = VP/E
M decreases
Damping factor:
2.2 2 1.8 1.6 1.4 1.2 1 0.8 0.6 0.4 0.2 0
K = dV/dtOFF/(E x 0)
M=1 M = 0.75 M = 0.5 M = 0.25 M=0
M decreases
Damping factor:
0 0.2 0.4 0.6 0.8 1 1.2 1.4 1.6 1.8 2
As shown on these two diagrams, the load resistance (R) helps to reduce dV/dtOFF and VP. The load impact is significant if the damping factor is higher than 0.2.
8/18
AN437
How to design snubber circuit for turn-off improvement
2.2
2.2.1
RC snubber circuit design
Is the snubber circuit required?
Without snubber circuit, the slope of reapplied voltage is limited by the TRIAC capacitance between anode and cathode junction. The oscillating circuit is constituted by the load, L and R, and the internal capacitance, CT, of the TRIAC. For example, the typical internal capacitances of 1 A, 12 A and 24 A TRIACs are respectively 12 pF, 90 pF and 180 pF (without direct voltage junction polarisation, worst case). Without snubber circuit and for most part of inductive loads, the damping factor () is generally lower than 1. For an underdamped oscillating circuit (0 < 1), the voltage variation across the TRIAC (VT(t)) is:
Equation 7
- · ·t · 0 VT ( t ) = E - E· cos( p ·t ) + · sin( p ·t ) .e 0 p
With damped natural resonance:
Equation 8
p = 0 . 1 -
2
For example, in the case of a 26 W drain pump (L = 2.4 H and R = 190 at 50 Hz) controlled by a Z0103 TRIAC (CT = 12 pF), the damping factor is close to zero ( = 2.1 x 104). For low damping factor, the normalized voltage rise slope K is equal to 1 (refer to Figure 8, lower graph). The maximum slope of reapplied voltage across the TRIAC is then:
Equation 9
dV / dt OFF ( V / s ) = 2 · VRMS ( V ) · sin( ) L ( H ) ·C T ( F ) · 10
-6
According to this formula, the estimated dV/dtOFF is equal to 59 V/s without snubber circuit. As shown in Figure 9, the measured dV/dtOFF is in fact about 10 V/s. The error between the Equation 9 result and real value is due to the fact that we didn't take into account the load inductance saturation (real value is higher at low current), the parallel parasitic capacitor of the load, the recovery current and the load resistance increase with frequency. Moreover, the turn-off measurement is done with a voltage probe which adds a 12 pF capacitor across the TRIAC. So, the measured dV/dtOFF is always lower than the theoretical value, given by Equation 9.
9/18
How to design snubber circuit for turn-off improvement Figure 9. Z0103 TRIAC turn-off on inductive load (26 W drain pump) without snubber circuit and in transient operating
VMains (100 V/div)
AN437
VP = 350 V dV/dtOFF = 10 V/ s
VT (100 V/div)
dI/dtOFF = 0.13 A/ms
IT (10 mA/div)
An RC snubber circuit must be used when there is a risk of TRIAC spurious triggering, i.e. when the measured dI/dtOFF and dV/dtOFF values are higher than the specified (dI/dt)c and (dV/dt)c values. In our application case and for the worst case load conditions (transient operating), the measured (dI/dt)OFF and (dV/dt)OFF values are equal respectively to 0.13 A/ms and 10 V/s. These values are higher than the specified (dI/dt)c and (dV/dt)c values, see Section 1.1.2. Thanks to an RC snubber circuit, rated in the next paragraph, the slope of the reapplied voltage could be limited and thus spurious triggering at turn-off could be avoided.
2.2.2
Resistor and capacitor snubber circuit design
The snubber circuit design depends on the damping factor (). When decreases, the snubber resistor and capacitor values decrease but the peak voltage and snubber circuit discharge current increase. Maximum instantaneous dV/dtOFF occurs at a time later than t = 0 when is lower than 0.5. When increases, the snubber resistor and capacitor values increase and the voltage overshoot decreases. The maximum instantaneous dV/dtOFF occurs at t = 0 when is higher than 0.5. Low damping factors are recommended. Indeed, thanks to the high voltage capability of TRIACs, the snubber circuit can be optimized to reduce the capacitor value and, in the same way, reduce the snubber circuit cost. To illustrate the RC snubber circuit design, a 26 W drain pump (L = 2.4 H and R = 190 at 50 Hz) controlled by a Z0103 TRIAC is considered. Two methods can be used to design the snubber circuit. The first method designs the RC snubber circuit with load resistance consideration. The second method considers pure inductive load. The first method of RC snubber circuit design is divided in four steps: 1. Snubber resistance choice To limit the TRIAC turn-on stress and optimize the TRIAC immunity against fast voltage transients, the snubber resistance is fixed to the minimum value. For Z01 TRIAC, the dI/dt at turn-on is limited to 20 A/s. The minimum snubber resistance value is 620 (refer to Section 1.4).
10/18
AN437
How to design snubber circuit for turn-off improvement Using Equation 6, the snubber circuit divider ratio M is equal to: M = 0.77 with R = 190 and RS = 620 2. Damping factor definition The snubber capacitor depends on the undamped natural resonance (0) and the damping factor (). Consider the following modified forms of Equation 4 and Equation 3:
Equation 4 modified
CS = 1 0 · L
2
with 0 =
dV / dt OFF E ·K
Where K is the normalized voltage rise slope (refer to the lower graphic in Figure 8).
Equation 3 modified
CS = 4 · L (R + R S )
2
· 2
From the two previous equations, the ratio between the normalized voltage rise slope (K) and the damping factor () is given by Equation 10. Figure 10, derived from the lower graph in Figure 8 gives the variation of this ratio with :
Equation 10
K = 2· L RS + R · dV / dt OFF E
For the drain pump controlled (L = 2.4 H and R = 190 at 50 Hz) and by using Equation 5, the final voltage value E is: E = 306 V for VRMS = 230 V and with 76 To avoid spurious triggering with Z0103 TRIAC, the dV/dtOFF is fixed to 2 V/s (lower than maximum allowed (dV/dt)c, see Figure 2). Thus according to Equation 10, the ratio between the normalized voltage rise slope and the damping factor is equal to 38. Figure 10 gives then the damping factor value ( = 0.026). Figure 10. Ratio between normalized voltage rise slope (K = dV/dtOFF / (E x 0)) and damping factor () according to the damping factor ()
100
K/
38
10
M decreases
1
M=1 M = 0.75 M = 0.5 M = 0.25 M=0
0.1 0.01
Damping factor:
= 0.026
0.1 1 10
11/18
How to design snubber circuit for turn-off improvement 3. Snubber capacitance and overvoltage calculations
L (R + R S ) 2 · x 2 ·10 » 9.9 nF with x = 0.026
9
AN437
The snubber capacitance is given by the modified form of Equation 3:
C S(nF) = 4 ·
The peak voltage is given in the upper graphic of Figure 8. A component with a 600 V capability will be suitable. VP = 1.92 · E 607 V with = 0.026. 4. RC snubber circuit validation The turn-off and turn-on behaviors must be checked experimentally to validate the designed RC snubber circuit. For turn-off commutation, the measured slope of the voltage rise is 1.7 V/s (Figure 10) and is very close to the theoretical slope (2 V/s). The measured peak voltage (520 V) is lower than the calculated value (607 V) due to the RLC model approximations (refer to Section 2.2.1). Figure 11. Z0103 TRIAC turn-off on inductive load with snubber circuit (C = 10 nF and R = 620 )
IT (10 mA/div)
VP = 520 V dI/dtOFF
VMains (100 V/div)
dV/dtOFF = 1.7 V/ s
VT (100 V/div)
The second method of RC snubber circuit design allows a quicker snubber capacitor choice. The capacitor is directly chosen from the load rms current (refer to Figure 12). Pure inductive loads are considered and the slope of the reapplied voltage is fixed to 2 V/s. For a given rms load current and according to the snubber resistance used (47 or 620 ), the ratio between the normalized voltage rise slope (K = dV/dtOFF / (E · 0)) and damping factor () is defined (refer to Equation 11). Then, as in the first snubber design method, the damping factor is given by Figure 10, the capacitor value by Equation 3 modified and the peak voltage by the upper graph of Figure 8.
12/18
AN437
How to design snubber circuit for turn-off improvement
Equation 11
K = 2· L RS + R · dV / dt OFF E with L = VRMS IRMS · 2 · · f
Figure 12. Snubber capacitor value and normalized peak voltage (Z = VP/E) according to the rms load current (assumptions: (dV/dt)OFF = 2.0 V/s and pure inductive load (worst case))
130 120 110 100 90 80 70 60 50 40 30 20 10 0
Snubber capacitor value (nF)
RS = 47 ohm
RS = 620 ohm
Load rms current: IRMS (A)
0 0.25 0.5 0.75 1 1.25 1.5 1.75 2 2.25 2.5 2.75 3 3.25 3.5 3.75 4
2 1.95 1.9 1.85 1.8 1.75 1.7 1.65 1.6 1.55 1.5
Normalized peak voltage (Z = VP/E)
RS = 47 ohm
RS = 620 ohm
Load rms current: IRMS (A)
0 0.25 0.5 0.75 1 1.25 1.5 1.75 2 2.25 2.5 2.75 3 3.25 3.5 3.75 4
Note:
For inductive load with rms current higher than 4 A, Snubberless TRIACs are recommended. In the case of a 26 W drain pump, the rms load current is 0.3 A in transient operating (worst case). The corresponding snubber capacitor value is about 10 nF, like defined previously. The estimated peak voltage is 613 V. The estimated peak voltage is 20% higher than the measured value due to the RLC model approximations (refer to Section 2.2.1) and because, in the application, the load is not purely inductive and the peak voltage is limited by the load resistance.
13/18
Conclusion
AN437
3
Conclusion
An RC snubber circuit is often used with TRIACs and presents different functions:
Aid circuit for turn-off commutation Fast transient voltage suppressor Over voltage limiter at turn-off commutation in case of inductive load with low rms current
The RC snubber circuit drawback is the turn-on stress induced by the capacitor discharge. Thanks to the high voltage capability of TRIACs, the snubber circuit design can be optimized in order to reduce the capacitor value and, in the same way, reduce the snubber circuit cost. Never theless, when low load inductances are controlled or, low damping factor or low slope of reapplied voltage are considered, the snubber circuit design can lead to choose a low snubber resistance value. To limit the snubber capacitor discharge through the TRIAC at turn-on, the resistor value must be higher than a minimum value (typically 47 for most TRIACs and ACSTs).
14/18
AN437
RLC series circuit step response explanation
Appendix A
RLC series circuit step response explanation
The RSCS snubber circuit and the load, L and R, make up a resonant circuit. The electrical circuit analyzed in this Appendix is shown in Figure 13 Figure 13. Application circuit and its equivalent diagram at turn-off commutation
Application circuit Load
L VMains G IG R IT VT RS CS VCs E
Equivalent diagram at turn-off commutation
Load L R
IT RS VT CS
Note:
In this Appendix the equations 1 to 6 are reproduced here with the same numbering to facilitate use of this application note. For a second order linear differential equation with a step function input, the voltage variation across the snubber capacitance (VCs(t)) and the TRIAC (VT(t)) is given by:
Equation 1
1 0
2
·
d V Cs ( t ) dt
2
2
+
2 . dV Cs ( t ) · + V Cs ( t ) = E 0 dt
Equation 2
VT ( t) = R S · C S · dV Cs ( t ) dt + V Cs ( t )
With damping factor:
Equation 3
=
(R S + R )( ) 2
·
CS (F ) L(H )
Undamped natural resonance:
Equation 4
0 ( rad / s ) = 1 L ( H ) ·C S ( F )
15/18
RLC series circuit step response explanation Final voltage value:
AN437
Equation 5
E= 2 · VRMS · sin( ) with sin( ) = L· 2 + (L · ) 2 R
V RMS : mains rms voltage
Snubber circuit divider ratio:
Equation 6
M= RS RS + R
The voltage variation (VT(t)) across the TRIAC depends on the damping factor coefficient. For each damping factor, the initial conditions to solve the differential equation are the same: At t = 0
Equation 12
dV T dt E·R S = L 0
At t = ¥
Equation 13
VT ( ) = E
Note:
The recovery current due to the storage charge is not considered in the initial conditions.
Underdamped oscillating circuit: 0 1
Equation 14
- · ·t .0 VT ( t ) = E - E· cos( p ·t ) + ( 2·(1 - M) - 1)· · sin( p ·t ) ·e 0 p
With damped natural resonance
Equation 15
p = 0 . 1 -
2
Damped oscillating circuit: = 1
Equation 16
VT ( t ) = E - E·(1 + ( 2·(1 - M ) - 1)·0 ·t ) ·e
- 0 ·t
With damped natural resonance
Equation 17
p = 0
16/18
AN437
Revision history Overdamped oscillating circuit: > 1
Equation 18
- · ·t .0 VT ( t ) = E - E· cosh( p ·t ) + ( 2 ·(1 - M) - 1)· · sinh( p ·t ) .e 0 p
With damped natural resonance
Equation 19
p = 0 .
2
-1
Thanks to these three equations and their derivatives, the variation between the peak voltage and the slope of the voltage rise can be defined according to the damping factor and the resistive load. The damping factor determines the shape of the voltage wave (refer to Figure 14). Figure 14. Voltage waves (VT(t)) for different damping factors () (assumption M = 1)
Triac voltage VT (t) (V)
700 600 500 400 300 200 100 0 0 0.25 0.5 0.75 1 1.25 1.5
decreases
î=0 î = 0.25 î = 0.5 î = 0.75 î=1 î = 1.5 E = final value
Time: t (s)
When is lower than 0.5, the voltage shape is not exponential and the maximum instantaneous slope of voltage rise occurs at a time later than t = 0. When is equal and higher than 1, some overshoots occur even if the oscillating circuit is damped and overdamped.
Revision history
Table 1.
Date 1995 22-Oct-2007
Document revision history
Revision 1 2 Initial release. Reformatted to current standards. Complete rewrite for text and graphics. Part numbers updated for current products. Changes
17/18
AN437
Please Read Carefully:
Information in this document is provided solely in connection with ST products. STMicroelectronics NV and its subsidiaries ("ST") reserve the right to make changes, corrections, modifications or improvements, to this document, and the products and services described herein at any time, without notice. All ST products are sold pursuant to ST's terms and conditions of sale. Purchasers are solely responsible for the choice, selection and use of the ST products and services described herein, and ST assumes no liability whatsoever relating to the choice, selection or use of the ST products and services described herein. No license, express or implied, by estoppel or otherwise, to any intellectual property rights is granted under this document. If any part of this document refers to any third party products or services it shall not be deemed a license grant by ST for the use of such third party products or services, or any intellectual property contained therein or considered as a warranty covering the use in any manner whatsoever of such third party products or services or any intellectual property contained therein.
UNLESS OTHERWISE SET FORTH IN ST'S TERMS AND CONDITIONS OF SALE ST DISCLAIMS ANY EXPRESS OR IMPLIED WARRANTY WITH RESPECT TO THE USE AND/OR SALE OF ST PRODUCTS INCLUDING WITHOUT LIMITATION IMPLIED WARRANTIES OF MERCHANTABILITY, FITNESS FOR A PARTICULAR PURPOSE (AND THEIR EQUIVALENTS UNDER THE LAWS OF ANY JURISDICTION), OR INFRINGEMENT OF ANY PATENT, COPYRIGHT OR OTHER INTELLECTUAL PROPERTY RIGHT. UNLESS EXPRESSLY APPROVED IN WRITING BY AN AUTHORIZED ST REPRESENTATIVE, ST PRODUCTS ARE NOT RECOMMENDED, AUTHORIZED OR WARRANTED FOR USE IN MILITARY, AIR CRAFT, SPACE, LIFE SAVING, OR LIFE SUSTAINING APPLICATIONS, NOR IN PRODUCTS OR SYSTEMS WHERE FAILURE OR MALFUNCTION MAY RESULT IN PERSONAL INJURY, DEATH, OR SEVERE PROPERTY OR ENVIRONMENTAL DAMAGE. ST PRODUCTS WHICH ARE NOT SPECIFIED AS "AUTOMOTIVE GRADE" MAY ONLY BE USED IN AUTOMOTIVE APPLICATIONS AT USER'S OWN RISK.
Resale of ST products with provisions different from the statements and/or technical features set forth in this document shall immediately void any warranty granted by ST for the ST product or service described herein and shall not create or extend in any manner whatsoever, any liability of ST.
ST and the ST logo are trademarks or registered trademarks of ST in various countries. Information in this document supersedes and replaces all information previously supplied. The ST logo is a registered trademark of STMicroelectronics. All other names are the property of their respective owners.
2007 STMicroelectronics - All rights reserved STMicroelectronics group of companies Australia - Belgium - Brazil - Canada - China - Czech Republic - Finland - France - Germany - Hong Kong - India - Israel - Italy - Japan Malaysia - Malta - Morocco - Singapore - Spain - Sweden - Switzerland - United Kingdom - United States of America www.st.com
18/18
|
